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Article(id=1266342915954597899, tenantId=1146029695717560320, journalId=1146031591421210625, issueId=1266342817036128371, articleNumber=null, orderNo=null, doi=10.3981/j.issn.1000-7857.2026.01.00117, pmid=null, cstr=null, oa=null, hot=null, price=null, onlineType=0, articleFormat=0, articleType=null, articleTypeStr=research-article, receivedDate=1769961600000, receivedDateStr=2026-02-02, revisedDate=1776700800000, revisedDateStr=2026-04-21, acceptedDate=null, acceptedDateStr=null, onlineDate=1779849278676, onlineDateStr=2026-05-27, pubDate=1778601600000, pubDateStr=2026-05-13, doiRegisterDate=null, doiRegisterDateStr=null, onlineIssueDate=1779849278676, onlineIssueDateStr=2026-05-27, onlineJustAcceptDate=null, onlineJustAcceptDateStr=null, onlineFirstDate=null, onlineFirstDateStr=null, sourceXml=null, magXml=null, createTime=1779849278676, creator=13701087609, updateTime=1779849278676, updator=13701087609, issue=Issue{id=1266342817036128371, tenantId=1146029695717560320, journalId=1146031591421210625, year='2026', volume='44', issue='9', pageStart='1', pageEnd='136', issueExtLink='null', onlineDate='null', pubDate='1778601600000', pubDateStr='2026-05-13', beforeIssueId=null, nextIssueId=null, price=null, status=1, issueComplete=1, articleOrder=1, issueType=-1, specialIssue=null, createTime=1779849255084, creator='13701087609', updateTime=1779849689565, updator='13701087609', preIssue=null, nextIssue=null, articleTotal=null, ext={EN=IssueExt(id=1266344639704485987, tenantId=1146029695717560320, journalId=1146031591421210625, issueId=1266342817036128371, language=EN, specialIssueTitle=, coverIllustrator=null, specialIssueEditor=, specialIssueAbout=), CN=IssueExt(id=1266344639708680292, tenantId=1146029695717560320, journalId=1146031591421210625, issueId=1266342817036128371, language=CN, specialIssueTitle=, coverIllustrator=null, specialIssueEditor=, specialIssueAbout=)}, issueFiles=null, downloadFileDto=null}, startPage=98, endPage=107, ext={EN=ArticleExt(id=1266342916868956173, articleId=1266342915954597899, tenantId=1146029695717560320, journalId=1146031591421210625, language=EN, title=Research and design of dual−band rectifying metasurface for ambient radio frequency energy harvesting, columnId=1150494644690366681, journalTitle=Science & Technology Review, columnName=Papers, runingTitle=null, highlight=null, articleAbstract=

In next−generation electronic information systems, ambient wireless energy harvesting (WEH) has emerged as a prominent research frontier. This work first presents a dual−band metasurface−based energy harvester leveraging an open split−ring resonator (SRR) architecture, achieving absorption efficiencies exceeding 90% at both 2.45 and 5.80GHz. Second, we propose a dual−band rectification system tailored for low−power−density environments, implemented via a single−stage voltage−doubler topology that jointly optimizes harmonic suppression and impedance matching. Under a load resistance of 800 Ω and an input power of 0 dBm, the RF−DC conversion efficiency reaches 53.5% at 2.45 GHz and 38.2% at 5.8 GHz. Third, a dual−band energy combining network is introduced to integrate the harvester and rectifier into a rectifying metasurface. Experimental validation confirms overall conversion efficiencies of 48.2% at 2.45 GHz and 37.7% at 5.8 GHz. Notably, the proposed rectifying metasurface maintains robust rectification performance over incident angles of ±40° at 2.45 GHz and ±30° at 5.8 GHz. Collectively, this design simultaneously addresses three critical challenges—low incident power sensitivity, dual−band operation, and wide−angle incident—demonstrating strong integration capability.

, authors=null, authorsList=Handong WU, Yuhui REN, Jianan ZHENG, authorCompany=null, correspAuthors=Yuhui REN, authorNote=null, correspAuthorsNote=null, copyrightStatement=All rights reserved. Unauthorized reproduction is prohibited., copyrightOwner=null, extLink=null, articleAbsUrl=null, sourceXml=null, magXml=null, pdfUrl=null, pdf=null, pdfFileSize=null, pdfExtLink=null, richHtmlUrl=null, mobilePdfUrl=null, reviewReport=null, pdfFirstPage=null, abstractGraph=null, abstractGraphContent=null, abstractVideo=null, citation=null, cebUrl=null, magXmlContent=null, mapNumber=null, fund=null), CN=ArticleExt(id=1266342924418703409, articleId=1266342915954597899, tenantId=1146029695717560320, journalId=1146031591421210625, language=CN, title=面向环境射频能量收集的双频带整流超表面研究与设计, columnId=1146540929516700224, journalTitle=科技导报, columnName=研究论文, runingTitle=null, highlight=null, articleAbstract=

在新一代电子信息系统中，环境中射频能量的收集已成为研究热点。设计了一款基于开口谐振环结构的双频超表面能量收集器，其在2个谐振频率（2.45和5.80 GHz）处的吸波效率都高达90%以上。提出了一款适用于低功率密度环境的双频整流系统，其采用单阶倍压整流电路，同时兼顾了谐波抑制和阻抗匹配。当负载电阻为800 Ω、输入功率为0 dBm时，电路在2.45和5.80 GHz处射频−直流转换效率分别为53.5%和38.2%。又设计了双频能量合成网络，将能量收集器与整流电路组合为整流超表面。实验结果表明，整流超表面在2个频点处的转换效率分别为48.2%和37.7%。此外，在2.45 GHz处，所提出的整流超表面在±40°入射角范围内具有良好的整流效果，在5.80 GHz处的入射角范围则为±30°。本研究设计统筹兼顾了低入射功率、双工作频段和宽入射角性能，具有良好的综合特性和广阔的应用前景。

, authors=

伍捍东，研究员，研究方向为微波技术与天线，电子信箱：

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任宇辉（通信作者），副教授，研究方向为超表面设计及应用，电子信箱：
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伍捍东，研究员，研究方向为微波技术与天线，电子信箱：

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伍捍东，研究员，研究方向为微波技术与天线，电子信箱：

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RL3/Ω2.45 GHz5.80 GHz
VDC /mVηRF−DC/%VDC/mVηRF−DC/%
3.714.3638.712.6830.2
1026.348.223.337.7
2334.936.830.427.8
3435.325.433.322.6
4738.822.336.119.3
7639.414.237.212.7
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PRF = 0 dBm时整流超表面的实测效率

, figureFileSmall=null, figureFileBig=null, tableContent=
RL3/Ω2.45 GHz5.80 GHz
VDC /mVηRF−DC/%VDC/mVηRF−DC/%
3.714.3638.712.6830.2
1026.348.223.337.7
2334.936.830.427.8
3435.325.433.322.6
4738.822.336.119.3
7639.414.237.212.7
), ArticleFig(id=1266342934942212215, tenantId=1146029695717560320, journalId=1146031591421210625, articleId=1266342915954597899, language=EN, label=null, caption=null, figureFileSmall=null, figureFileBig=null, tableContent=
RL3/Ω2.45 GHz5.80 GHz
VDC /mVηRF−DC/%VDC/mVηRF−DC/%
3.752.050.747.442.2
1093.157.289.951.1
23128.449.8123.045.7
34135.337.4130.034.6
47138.428.3132.626.0
76146.019.5135.216.7
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PRF = 10 dBm时整流超表面的实测效率

, figureFileSmall=null, figureFileBig=null, tableContent=
RL3/Ω2.45 GHz5.80 GHz
VDC /mVηRF−DC/%VDC/mVηRF−DC/%
3.752.050.747.442.2
1093.157.289.951.1
23128.449.8123.045.7
34135.337.4130.034.6
47138.428.3132.626.0
76146.019.5135.216.7
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面向环境射频能量收集的双频带整流超表面研究与设计
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伍捍东 1 , 任宇辉 2, * , 郑佳楠 3
科技导报 | 研究论文 2026,44(9): 98-107
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科技导报 |研究论文 2026 , 44 (9) : 98 -107
面向环境射频能量收集的双频带整流超表面研究与设计
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伍捍东1 , 任宇辉2, * , 郑佳楠3
作者信息
  • 1西安恒达微波技术开发有限公司，西安 710100
  • 2西北大学电子信息学院，西安 710127
  • 3中国电子科技集团公司第三十九研究所，西安 710065
通讯作者:
任宇辉（通信作者），副教授，研究方向为超表面设计及应用，电子信箱：
Research and design of dual−band rectifying metasurface for ambient radio frequency energy harvesting
Handong WU1 , Yuhui REN2, * , Jianan ZHENG3
Affiliations
  • 1Xi'an HengDa Microwave Technology Development Co., Ltd., Xi'an 710100, China
  • 2School of Electronic Information, Northwest University, Xi'an 710127, China
  • 3Northwest Institute of Electronic Equipment (NWIEE), Xi'an 710065, China‌
出版时间: 2026-05-13 doi: 10.3981/j.issn.1000-7857.2026.01.00117
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摘要
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在新一代电子信息系统中，环境中射频能量的收集已成为研究热点。设计了一款基于开口谐振环结构的双频超表面能量收集器，其在2个谐振频率（2.45和5.80 GHz）处的吸波效率都高达90%以上。提出了一款适用于低功率密度环境的双频整流系统，其采用单阶倍压整流电路，同时兼顾了谐波抑制和阻抗匹配。当负载电阻为800 Ω、输入功率为0 dBm时，电路在2.45和5.80 GHz处射频−直流转换效率分别为53.5%和38.2%。又设计了双频能量合成网络，将能量收集器与整流电路组合为整流超表面。实验结果表明，整流超表面在2个频点处的转换效率分别为48.2%和37.7%。此外，在2.45 GHz处，所提出的整流超表面在±40°入射角范围内具有良好的整流效果，在5.80 GHz处的入射角范围则为±30°。本研究设计统筹兼顾了低入射功率、双工作频段和宽入射角性能，具有良好的综合特性和广阔的应用前景。

无线能量收集  /  整流超表面  /  能量合成  /  谐波抑制电路

In next−generation electronic information systems, ambient wireless energy harvesting (WEH) has emerged as a prominent research frontier. This work first presents a dual−band metasurface−based energy harvester leveraging an open split−ring resonator (SRR) architecture, achieving absorption efficiencies exceeding 90% at both 2.45 and 5.80GHz. Second, we propose a dual−band rectification system tailored for low−power−density environments, implemented via a single−stage voltage−doubler topology that jointly optimizes harmonic suppression and impedance matching. Under a load resistance of 800 Ω and an input power of 0 dBm, the RF−DC conversion efficiency reaches 53.5% at 2.45 GHz and 38.2% at 5.8 GHz. Third, a dual−band energy combining network is introduced to integrate the harvester and rectifier into a rectifying metasurface. Experimental validation confirms overall conversion efficiencies of 48.2% at 2.45 GHz and 37.7% at 5.8 GHz. Notably, the proposed rectifying metasurface maintains robust rectification performance over incident angles of ±40° at 2.45 GHz and ±30° at 5.8 GHz. Collectively, this design simultaneously addresses three critical challenges—low incident power sensitivity, dual−band operation, and wide−angle incident—demonstrating strong integration capability.

wireless energy harvesting  /  rectifying metasurface  /  energy synthesis  /  harmonic suppression circuit
伍捍东, 任宇辉, 郑佳楠. 面向环境射频能量收集的双频带整流超表面研究与设计. 科技导报, 2026 , 44 (9) : 98 -107 . DOI: 10.3981/j.issn.1000-7857.2026.01.00117
Handong WU, Yuhui REN, Jianan ZHENG. Research and design of dual−band rectifying metasurface for ambient radio frequency energy harvesting[J]. Science & Technology Review, 2026 , 44 (9) : 98 -107 . DOI: 10.3981/j.issn.1000-7857.2026.01.00117
正文
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随着新一代电子信息技术的飞速发展，通信网络、计算机网络和各种感知系统渐渐融合，大千世界的万物互联逐步成为现实。但随之而来的是大量传感器节点和智能终端设备的供电问题。给这些广泛分布的电子设备供电，既要考虑时效性和便捷性，又要避免环境污染的风险。因此，从自然环境中收集能量，如电磁射频能量，已成为解决这个问题的最有前景的方法之一[1−2]。目前，环境中的射频能量越来越丰富，适用于多种无线通信与感知系统的电磁波广泛分布。这些能量除了少部分用来传输信息外，大部分都耗散在空间中。一般而言，射频能量在环境中的功率密度稳定在2 μW/cm2~100 mW/cm2的范围内，且不受空间、时间、天气的影响。因此，射频无线能量收集（wireless energy harvesting，WEH）技术完全能够满足传感器等低功耗电子设备的供能需求。
在传统的WEH系统中，一般将天线作为射频接收部分的前端器件，其与匹配电路、整流电路结合后统称为整流天线[3−5]。近年来，研究人员借鉴了Landy等[6]于2008年提出的超材料完美电磁吸波器的创意，设计了WEH超表面取代前端天线[7−10]。和传统天线相比，首先，超表面阵列中亚波长尺寸的单元紧密排列，具有强谐振效应，增强了本构参数和滤波效应，所以其具有更高的能量收集效率。其次，超表面单元容易实现多模谐振效应，便于实现多频段的无线能量收集。最后，亚波长的单元一般具有紧凑化、小型化和旋转对称的结构特点，所以在能量收集时表现出极化不敏感和宽入射角等优点。Ramahi等[7]首次设计了WEH超表面，单元采用开口谐振环（split ring resonators, SRR）。Yu等[8]设计了一种中心对称的扇形WEH超表面，具有极化不敏感特性和宽入射角特性。Ghaderi等[9]采用编码超表面设计，可以实现高效的双频能量收集。Ghaneizadeh等[10]采用二维各向同性柔性材料设计超表面，可以提高WEH超表面与应用环境的共形能力。
这里需要说明，尽管无WEH超表面研究的灵感出自超材料吸波器，但能量收集器需要将捕获的射频能量高效汇集于端口，然后进行整流、存储和管理，而不是像吸波器那样将能量耗散。更重要的是，只有将WEH超表面和整流网络相结合组成整流超表面，才能实现能量收集的完整功能链路，其基本结构如图1所示。
显然，整流超表面的设计主要有2方面的工作，即WEH超表面和整流网络。Amin等[11]采用4个L形谐振器组成WEH超表面单元，输入功率为17.8 dBm时，最大能量转换效率达到55%。Erkmen等[12]设计的超表面单元是领结形交叉偶极子，当输入功率为15 dBm时，最大的能量转换效率达到61%。但是这2个整流超表面都需要较大的入射功率才能实现最大的能量转换效率。相比较而言，Lee等[13]提出的电感电容式单元（electric−inductive−capacitive，ELC）和倍压整流电路组成的整流超表面，在低输入功率（0.4 dBm）时，实现了76.8%的能量转换效率。Aldhaeebi等[14]在环形单元的金属臂之间添加1个二极管来实现整流，在低输入功率的条件下实现80%的能量转换效率。不过，上述研究都只能在单一频段工作。Li等[15]通过在矩形贴片上开槽来实现按双频吸波，其可以在2.4和5.8 GHz处分别实现58%和50%的能量转换效率。Yu等[16]以8个不对称偶极子作为超表面单元，在2.2~2.7 GHz频段内实现90%的能量转换。但是这2项工作中的整流超表面不具备宽入射角特性。文献[17−20]提出的宽频和多频整流超表面都具有宽入射角特性和较高的能量转换效率，然而单元设计较为复杂。
本研究提出了一款适用于无线能量收集系统的双频整流超表面，设计兼顾低感应功率灵敏度、双频段工作以及宽角度入射等特性，具有均衡的综合性能，以及在无线供能的物联网和传感应用中实际部署的巨大潜力。
1 双频整流超表面的结构与设计
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本研究设计的双频整流超表面的基本结构如图2所示，共分为5层。最上层是24×24个单元组成的无线能量收集超表面，其附着在介电常数为3.5的聚四氟乙烯玻璃布板（F4B）上。第3层是金属地板，第4层是介电常数为2.65的F4B基板。最底层是射频能量合成网络与整流系统。射频能量合成网络包括功分器和阻抗变换器。整流系统又包括整流电路、谐波抑制电路和阻抗匹配电路。
1.1 超表面单元
本研究设计的WEH超表面单元的基本结构如图3（a）所示，其由并联的SRR、介质基板、金属地板和金属连接柱构成。SRR具有较强的谐振特性，可以实现高效率的吸波，并将捕获的射频能量转换为感应电流。介质基板的损耗角正切为0.001，厚度为3 mm。为了传导与汇聚SRR激发的感应电流，通过金属柱将顶部、底部的金属层与吸收负载RL1进行连接。需要说明的是，在后续的设计中，RL1会被具有相同输入阻抗的整流系统代替。单元的具体尺寸如下：w=20 mm，w1=19 mm，w2=4.5 mm，w3=2.9 mm，w4=0.5 mm，w5=0.4 mm，g=0.5 mm，d=0.25 mm。
图3（b）为所设计单元结构的等效电路，方形谐振环上的开口缝隙有等效电容C，金属臂上有等效电感L，所以一个SRR环可等效为一个串联谐振电路。将2个不同大小的环并联，可以实现双频能量收集。由图可知
$ \begin{split} & \frac{1}{Z\mathrm{_{in}}}=\frac{1}{Z_1}+\frac{1}{Z_2}, \\ &Z_1=\frac{1}{\mathrm{j}\omega}\times \frac{\left(1-\omega^2C_1L_1\right)\left(1-\omega^2C_2L_2\right)}{C_1\left(1-\omega^2C_2L_2\right)+C_2\left(1-\omega^2C_1L_1\right)}, \\ &Z_2=Z_T+R_{L1}\end{split} $
式中，Zin表示超表面单元等效输入阻抗，L1、L2、C1、C2分别表示内环和外环等效电感和电容，ZT表示介质板的特征阻抗。
为了产生串联谐振，需要保证Im（Zin）=0，由此可得超表面单元谐振角频率ω0为
$ {\omega _0}{\text{ = }}\sqrt {\frac{{{C_1}+{C_2}}}{{{C_1}{C_2}\left( {{L_1}+{L_2}} \right)}}} $
因此，可以通过改变超表面单元的尺寸来改变等效电容和电感，进而调控其工作频率。使用CST Studio Suite对单元进行仿真分析，图4所示为SRR主要参数对反射系数（|S11|）大小的影响。可见低频和高频谐振频率都随着w1的增大而减小，且都随着w2的增大而增大，这说明外环的尺寸对低频和高频谐振都有较大的影响。高频谐振频率随着w3的增大而减小，而低频谐振频率没有变化，这说明内环只影响高频谐振点。由于外环的尺寸明显大于内环，所以其对超表面单元的谐振频率具有更强的影响力。
图4（d）为反射系数与负载RL1之间的变化关系。在保证单元尺寸不变的前提下，当RL1从60 Ω增大到100 Ω时，超表面的反射系数逐渐减小，匹配越来越好。但当RL1大于100 Ω时，反射系数又逐渐增大，所以在本设计中选定RL1=100 Ω作为最优负载。
可以将超表面单元看作一个双端口网络，其能量吸收效率可以用A（ω）来表示，定义为
$ A(\omega ) = 1 - R(\omega ) - T(\omega ) = 1 - |{S_{11}}{|^2} - |{S_{21}}{|^2} $
式中，$ R(\omega ) $代表超表面单元的反射率，$ T(\omega ) $代表透射率，|S11|和|S21|分别表示反射系数和传输系数的大小。
仿真超表面单元的S参数，由公式（3）计算其能量吸收效率。需要说明的是，本设计中单元的背面是金属接地板，所以|S21|近似等于0。由图5可知，在2.45和5.80 GHz 2个频点处的入射波几乎都被超表面单元吸收，整体吸收效率达到99.6%和99.3%。这其中被负载RL1吸收的效率分别为95.4%和95.7%，只有4.2%和3.6%的能量被金属贴片和介质损耗掉，这既体现了超表面吸波器和能量收集器的区别，又证明了RL1的选择是较优的。
定义电磁波入射方向与Z轴的夹角为入射角θ，图6所示为不同入射角时超表面单元的能量吸收效率。可见随着电磁波入射角度的增大，双频超表面单元的吸收效率逐渐降低。总体而言，当工作频率为2.45 GHz，且入射角在±65°之间变化时，吸波效率保持在50%以上；当工作频率为5.80 GHz，且入射角在±40°之间变化时，效率保持在50%以上。说明该结构在2个频点处具有宽角入射特性。
1.2 射频功率合成网络
自然环境中射频信号十分微弱，而且单个超表面单元的尺寸较小，能接收到的能量十分有限，所以本设计中采用2×2的双频功率合成网络来实现高效能量收集。如图7（a）和图7（b）所示，功率合成网络包括一分四路T型功分器和阻抗变换器。4个超表面单元通过端口P2−P5连接到功分器上，超表面单元的等效阻抗（100 Ω）经过了2个T型结在端面A处变换为25 Ω，然后再连接双频阻抗变换器到端口P1处变换为50 Ω。如前所述，功率合成网络介质板使用介电常数为2.65的F4B材料，损耗角正切为0.001，厚度为0.5 mm。
图7（c）为双频阻抗变换器的等效电路，l1和l2为两端串联微带传输线，l3是一段并联的开路调配线，Z1~Z3表示各段传输线的特性阻抗。为了简化计算，取l1=l2=l。由传输线理论可知
$ \begin{split} & \frac{1}{Z_0}=\frac{1}{Z_B}+\frac{1}{Z_C},\; Z_A=Z_1\frac{2Z_0+\mathrm{j}Z_1\tan\beta l}{Z_1+2\mathrm{j}Z_0\tan\beta l}, \\ &Z_B=Z_2\frac{Z_A+\mathrm{j}Z_2\tan\beta l}{Z_2+\mathrm{j}Z_A\tan\beta l},\; Z_C=\frac{Z_3}{\mathrm{j}\tan\beta l_3}\end{split} $
式中，ZA表示l1段传输线相对P1端口的输入阻抗，ZB表示l1和l2段传输线相对P1端口的输入阻抗，ZC表示l3段开路线的输入阻抗。
利用文献[21]中的限制条件
$ \frac{{{Z_2} - {Z_1}{{\tan }^2}\beta l}}{{\left( {{Z_1}+{Z_2}} \right)\tan \beta l}} = \frac{{{Z_2}\tan \beta {l_3}}}{{{Z_3}}} $
可求得双频阻抗变换器的相关参数
$ {Z}_{1}=\sqrt{2}{Z}_{0}\mathrm{tan}\beta l,\;{Z}_{2}=\frac{\sqrt{2}{Z}_{0}}{\mathrm{tan}\beta l},\;{Z}_{3}=\frac{\sqrt{2}{Z}_{0}\mathrm{tan}\beta {l}_{3}}{1-{\mathrm{tan}}^{2}\beta l} $
本设计中设定Z0=25 Ω，最终经过理论计算和仿真优化得到双频功率合成网络的详细尺寸如下：w6=0.35 mm，w7=1.32 mm，w8=3.5 mm，w9=0.2 mm，w10=3.2 mm，w11=1.6 mm，l1=l2=13 mm，l3=26 mm。
图8（a）所示为双频功率合成网络的S参数曲线。将2×2个超表面单元合成的一个子阵列与功率合成网络相结合，进行联合仿真，图8（b）所示为子阵列的能量收集效率，可见在2.45和5.80 GHz这2个频点上，子阵列的效率分别可以达到94.7%和94.3%。
1.3 双频整流系统
双频整流系统的基本结构如图9（a）所示，其主要包括整流电路、谐波抑制电路和阻抗匹配电路3部分。系统的输出端接直流负载RL2，其最优值需要仿真优化得到。整流系统的介质材料和前面双频合成网络一样，均为厚度为0.5 mm的F4B材料。为了简化整个能量合成网络，同时减小能量损耗，最终优化后设计每个双频整流系统的输入端接2个2×2子阵列，如图9（b）所示。
1.3.1 整流电路
整流电路是双频整流系统的核心组成部分，其设计的关键是电路拓扑结构和整流二极管的选择。本设计中选用单阶倍压整流电路，能够在较宽的输入功率范围内保持良好的整流效率和较高的输出电压。目前在电磁能量收集应用中使用最广泛的整流二极管是肖特基势垒二极管，其导通电压低、工作频率高，且在微波频段具有高速切换的能力。在ADS（advanced design system）软件中，采用单阶倍压的拓扑结构对常见肖特基二极管的性能进行仿真，其整流效率随输入功率的变化关系如图10所示。从图中可以看出，当输入功率小于5 dBm时，HSMS−2850的整流效率相对较优，更适合构建低输入功率下的整流电路。这也正是本设计中的选择。需要说明，整流电路中的隔直电容C1和C2均为100 pF。
1.3.2 谐波抑制电路
经过整流电路后，输入射频信号转化为直流，但由于二极管的非线性，输出的直流信号会伴随有高次谐波分量。为了在终端负载上获得稳定的直流能量，需要在整流电路和负载之间增加一个直通滤波器来完成谐波抑制，其作用是抑制或反射直流能量中的高次谐波分量。为了简化电路的设计，这里只考虑基波和二阶谐波分量的抑制。
本设计中采用加载扇形枝节的微带滤波器实现谐波抑制的功能。为了实现双频整流系统的小型化，设计中仅用3个扇形开路枝节实现对这4个频率波的抑制，其基本结构如图11（a）所示，相关的尺寸参数为：w17=1.32 mm，l4=12 mm，l5=5.5 mm，l6=2 mm，l7=2 mm，l8=2 mm。此外，3个扇形开路枝节张角均为120°。双频谐波抑制网络的仿真S参数如图11（b）所示。可见信号在基频和二次谐波，即2.45、4.90、5.80和11.60 GHz处的衰减（|S21|）依次为−43.9、−27.3、−37.6和−31.1 dB。说明所设计的电路具有良好的带阻特性，能够对信号的基频和二次谐波起到良好的抑制作用。
1.3.3 双频阻抗匹配网络
图12所示为输入功率为0 dBm时，前述单阶倍压整流电路的输入阻抗和工作频率之间的关系。可见当工作频率为2.45和5.80 GHz时，整流电路的输入阻抗分别为（85.4− j77.8） Ω 和 （18.7−j26.6） Ω。如前所述，图7（b）中端口P1处的阻抗为50 Ω。因此，在功率合成网络和整流电路之间，设计了双频阻抗匹配网络，其兼具低通滤波和阻抗匹配2种功能。
双频阻抗匹配网络基本结构如图13（a）所示，其中开路线段l10 与l13用来匹配整流电路阻抗的虚部。由图13（b）可知，当Zin=（85.4−j77.8）Ω时，双频阻抗匹配网络的反射系数在2.45 GHz时最优。而当Zin=（18.7− j26.6）Ω，在5.8 GHz时，反射系数最小。最终得到双频阻抗匹配网络的详细尺寸如下：w18=3.2 mm，w19=0.2 mm，w20=0.3 mm，w21=1.0 mm，w22=0.2 mm，l9=6 mm，l10=3 mm，l11=4 mm，l12=12 mm，l13=26 mm。
1.3.4 双频整流系统整体性能
在完成各部分的设计后，对图9（a）所示整流系统进行原理图与版图联合仿真，并加工实物进行测试。图14（a）所示为整流系统的|S11|曲线，实测得到的谐振频率分别为2.48和5.86 GHz，与仿真的2.45 GHz和5.80 GHz基本一致。图14（b）所示为Pin=0 dBm时，整流效率随着RL2的变化趋势。可以看出当RL2在600~1200 Ω的范围内时，电路的整流效率保持稳定，但是当RL2大于1200 Ω时，整流效率出现了明显的下降趋势，本设计中最终选定RL2=800 Ω。图14（c）所示为RL2=800 Ω时，双频整流电路的效率随着输入功率的变化情况。可以看出随着输入功率的提高，整流效率有一个逐渐升高的趋势，但是当输入功率高于10 dBm时，其又有了明显的衰减。当输入功率为5~10 dBm时，电路在2.45和5.80 GHz处，都有50%以上的整流效率。此外，当RL2=800 Ω，Pin=10 dBm时，双频整流电路在2.45 GHz的最佳整流效率为60.2%，在5.80 GHz的最佳效率为56.1%。
2 系统测试与分析
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为了验证所设计双频整流超表面的性能，加工了24×24个单元组成的试验件进行测试。测试原理框图和实测场景如图15所示，实验中还用到了射频信号源、功率放大器、发射天线、万用表和拱形架等设备。
设定信号源的输出功率Pout =−10 dBm，经增益GA =30 dB的功率放大器后，将Pt =20 dBm的信号馈入喇叭天线。喇叭天线的增益为Gt=18 dB。为了保证整流超表面上的入射功率为PRF =0 dBm，即2×2子阵列上功率密度Sr = 62.5 μW/cm2，根据公式
$ S_{\text{r}}=\frac{P_{\text{t}}G_{\text{t}}}{4{\text{π}}L^2} $
可求得喇叭天线和整流超表面之间的距离L ≈ 0.89 m。类似地，当PRF =10 dBm时，可求得L ≈ 0.28m。
整流超表面将吸收到的电磁波转换为直流的效率（ηRF−DC）为
$ \left. \begin{gathered} {\eta _{{\text{RF - DC}}}} = \frac{{{P_{{\text{AC}}}}}}{{{P_{{\text{RF}}}}}} \times \frac{{{P_{{\text{DC}}}}}}{{{P_{{\text{AC}}}}}} \hfill \\{{P_{{\text{RF}}}} = {S_{\text{r}}} \times {A_{\text{p}}}} \hfill \\ \end{gathered} \right\} \Rightarrow {\eta _{{\text{RF - DC}}}} = \frac{{V_{{\text{DC}}}^2}}{{{R_{L2}}{S_{\text{r}}}{A_{\text{p}}}}} $
式中，Ap表示超表面子阵列的面积，PRF表示到达超表面的射频功率，PAC表示超表面感应到的交流功率，PDC表示整流超表面输出的直流功率，VDC表示电阻输出负载电阻RL3两端的测量电压。
如前分析，单个整流电路的最佳负载值为800 Ω。分析整个阵列的串−并联关系，整流超表面的输出端负载RL3 ≈ 6 Ω。表1和表2中分别给出了当PRF = 0 dBm和10 dBm时，不同RL3对应的输出电压及ηRF−DC。从表1中可以看出，当RL3 =10 Ω时，ηRF−DC在2.45和5.80 GHz处的最佳值分别为48.2%和37.7%。从表2中可以看出当RL3 =10 Ω时，ηRF−DC在2个频点处的最佳值分别为57.2%和51.1%。需要说明的是，在实验测试时用10 Ω的电阻代替了理论计算的6 Ω。
图16所示为当PRF = 0 dBm时，不同入射角下整流超表面的转换效率。可见当f=2.45 GHz时，整流超表面的效率在0°~40°的入射角范围内变化较为平缓。当入射角大于40°时，效率急剧下降。当f=5.80 GHz时，效率平缓变化的范围减小为0°~30°。显然，和图6的仿真结果比较，整流超表面的宽入射角特性有所恶化。分析原因，一方面，仿真时模拟的是无限大周期边界，而实测时阵面大小有限；另一方面，这可能是由实验条件及加工误差导致的。
3 结论
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传统整流天线作为微波无线能量收集系统的接收部分时增益较低，且难以保持高转换效率。针对这些不足，本研究实现了具有高收集效率和宽入射角特性的双频整流超表面。首先，利用具有强谐振特性的并联SRR结构加以金属柱进行能量收集，该结构在2.45和5.80 GHz处的吸收效率都高达90%以上，且具有宽入射角特性。此外，还设计了一款用于低功率密度环境下的双频整流电路，并将超表面阵列与整流电路整合并加工实测。结果显示，该整流超表面具有电磁能量收集与整流性能且具有宽入射角特性，当工作频率为2.45 GHz时，入射波在±40°的角度范围内具有高RF−DC效率；当工作频率为5.80 GHz时，入射角在±30°范围内RF−DC效率稳定。
基金
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  • 咸阳市重点研发计划项目(L2025−ZDYF−KTH−006)
文献
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2026年第44卷第9期
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doi: 10.3981/j.issn.1000-7857.2026.01.00117
  • 接收时间：2026-02-02
  • 首发时间：2026-05-27
  • 出版时间：2026-05-13
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  • 收稿日期：2026-02-02
  • 修回日期：2026-04-21
基金
咸阳市重点研发计划项目(L2025−ZDYF−KTH−006)
作者信息
    1西安恒达微波技术开发有限公司，西安 710100
    2西北大学电子信息学院，西安 710127
    3中国电子科技集团公司第三十九研究所，西安 710065

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任宇辉（通信作者），副教授，研究方向为超表面设计及应用，电子信箱：
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